We use assembly number A2088 for a family of amplifiers, shapers, high-voltage filters and photomultiplier (PMT) mounting circuits.
|A2088A||Amplifier-Shaper, Version One|
|A2088B||High-Voltage Low-Pass Filter|
|A2088C||SiPM Head, Version One|
|A2088D-0||Amplifier-Shaper, Version Two, No Shaper, L3 = 0 nH, C9 = 0 nF|
|A2088D-20||Amplifier-Shaper, Version Two, 20-ns Shaper, L3 = 100 nH, C9 = 1 nF|
|A2088D-50||Amplifier-Shaper Version Two, 50-ns Shaper, L3 = 3.3 μH, C9 = 1 nF|
We describe each letter version below. We present our initial work on using Silicon Photomultipliers (SiPMs) in Heller et al.. The SiPMs we are working with come from a family made by On Semiconductor, the MICROFC series.
[13-FEB-19] The A2088A is our first amplifier-shaper. Printed circuit board files in A208801B. The A208801A we aborted because we omitted C7 and C8.
We load two ERA-1SM into the circuit as shown. We measure gain versus frequency for various input powers.
We expect the gain to be +12 dBm for each amplifier, −3 dB for the attenuator, is +21 dB. We see up to 19 dB. The amplifier does not produce the +12 dBm output power we expect. We apply a 50-mVpp, 200 kHz input and observe the following output.
For inputs greater than 20 mVpp the amplifier oscillates and its gain at the signal frequency is compromised. Our maximum output amplitude is around 300 mVpp when we expect 3 Vpp.
The shaper we configure after consulting our treatise on pulse shapers. We set L1 = 3.3 μH and C3 = 1 nF. We find that the 100-nF capacitors cause the output baseline to shift. When combined with a 50-&Ohm; signal impedance, thes capacitors introduce a 5-μs time constant. During a 100-ns pulse, we expect the baseline voltage to move up by 2% of the pulse height. We observe something closer to 10%. We place 1-μF capacitors in parallel with the 100-nF coupling capacitors and get the following pulse.
[14-MAR-19] We work on the A2088A until it stops oscillating. We have 100-pF coupling capacitors, and for decoupling the power supply we have 100 pF, 100 nF and 1 μF capacitors scattered about. We have top-side ground planes made of copper tape. We have U1 as ERA-3SM and U2 as ERA-1SM, the attenuator is −3 dB, and L1 = 0 H, while C3 is omitted.
We apply 100 MHz input and obtain the following plot of output power and gain versus input power in dBm (decibels above 1 mW into 50 Ω).
Each of our four 100-pF coupling capacitors have impedance 15 Ω at 100 MHz, so each of them introduces a loss of 0.4 dB. The ERA-3SM and ERA-1SM should provide gain of around 34 dB. Our attenuator is −3 dB. We expect a total gain of around 29 dB. We observe 23 dB. We expect a maximum output of +12 dBm and that's what we see: 2.2 Vpp into our 50-Ω oscilloscope input.
We add 1-μF capacitors in parallel with all four 100-pF coupling capacitors, and two 10-μF capacitors in parallel with our existing decouplers. At 100 MHz with 70 mVpp input, our output is 1.9 Vpp for gain 29 dB. We measure gain versus frequency.
We load 3.3 μH for L1 and 1.0 nF for C3 to make our shaper. We obtain the following for a 200-mV input pulse.
The exact shape of the output pulse, and the amplitude of the small pre-pulse spike, depend upon the arrangement of our coaxial cables near the oscilloscope.
[01-FEB-19] The A2088B is a low-pass filter for a PMT high-voltage power supply. The high-voltage input, up to 3 kV, is low-pass filtered to remove noise, with corner frequency 4 kHz. SHV plugs receive and transmit the high-voltage power. The 10-kΩ series resistor will drop the high-voltage output by 10 V per 1 mA.
A side port with BNC socket provides a high-pass filtered view of the output high-voltage, with corner frequency 400 Hz. The filter proves effective in removing 100-kHz pulses from the high-voltage, and reducing PMT output noise by around 80%.
[11-FEB-19] Our silicon photomultiplier (SiPM) Head provides a 6 mm × 6 mm area, 35-μm pixel MICROFC-60035 photomultiplier along with bias and output coupling.
The A2088C-0 is a breadboard version shown below.
We use A2088C-0 to measure dark current versus bias voltage.
The A2088C-1 uses the A208801C printed circuit board. We have L1 omitted, C2 replaced with 1-Ω resistor, and R1 is 1 kΩ.
[09-DEC-19] We use the A2088C built on A208801C circuit board to detect light pulses emitted by an LED [Need part number, size, wavelength] driven by 12-ns pulses from a function generator. We amplify and shape the pulses emerging from the SiPM with an A2088D-100 (100-ns pulse duration and gain ×40).
[11-DEC-19] Suppose photons arrive at the top surface of the avalanche region of our SiPM, as yet unabsorbed, and now have some chance of being absorbed for each incremental distance they penetrate into the avalanche region. Let us assume the electric field is uniform through the thickness of the avalanche region, and assume a maximum avalanche gain of one million. We will get single-photon pulses all of the same height only if all photons are absorbed in the first infinitesimal layer of the avalanche region. But there will be some absorption depth for photons in the silicon, and photons absorbed deeper into the silicon will generate a smaller avalanche, and therefore a smaller pulse. We perform a Monte-Carlo simulation of this process using a Toolmaker script.
For the same plot made for 2% absorption length see Sim_1_2 and for 5% absorption length see Sim_1_5. The spread of pulse heights increases as the photons penetrate further. If we increase the gain to 107 the graph looks much the same.
Let us assume that thermal electrons are generated at random in the avalanche layer, with uniform distribution. We write a Monte-Carlo simulation of this process using another script and obtain the following plot of the thermal pulse rate distribution with respect to pulse height for three different values of maximum gain. We make our histogram with logarithmic bins so we can plot pulse height on a log scale.
The number of pulses in each decade of pulse height is the same, which is consistent with each decade corresponding to its own layer in the avalanche region, and all layers being of the same thickness.
[20-MAR-19] Our second amplifier-shaper has four copper layers. On the top layer are signals. On the first middle layer is the ground plane. On the second middle layer is a power plane. The bottom layer is for test points.
We add more attenuators to give us more freedom to alter the total gain of the circuit, and optimise its dynamic range for large and small inputs. Dual coupling capacitors expand the bandwidth down to 3 kHz, while at the same time providing reliable coupling to the attenuators at frequencies 1-10 GHz, where oscillations might otherwise arise. The resistors R9 and R10 allow us to match the input of the shaper more exactly to the PMT signal cable, so we can reduce the reflections that come back from the high-impedance PMT output. Inductors in the bias impedance of the two amplifiers further restrict the penetration of 1-10 GHz oscillating currents into the power supplies, reducing coupling between the two stages at these frequencies.
[25-MAR-19] The A208801D printed circuit board has four layers: top, ground, power, and bottom. The bottom layer we use only for pads and vias, and a token track to make identify the layer as a positive image. Printed circuit board A208801D, shown here.
[24-APR-19] We have our first assembled Amplifier-Shaper A2088D. We have U1 = U2 = ERA-3SM, R1-R4 3dB, L3 = 3.3 μH and C9 = 1.0 nF. Looking at the response to a 20-mV 12-ns pulse, We see signs of oscillation on OUT, and gain varies by a factor of two as we touch the circuit board. We replace L2 = 100 nH with L2 = 0.0 nH. The oscillations stop and the gain is stable.
[10-JUN-19] We report on the linearity and dynamic range of the V2 shaper in V2 Shaper-Amplifier Performance.
[26-JUN-19] The A2088D with C8 = 1.0 nF and C7 = 1.0 μF produces a sustained oscillation of 200-300 MHz at its output with amplitude of order 10 mVpp. We remove C8 and the output noise drops to 2 mVpp, with no obvious oscillations. The 1.0 μF ceramic capacitor in place of C7 is the CGA4J3X7R1H105K125AB with self-resonant frequency 5 MHz and equivalent series resistance 1 Ω at 100 MHz.
We mount the A2088D in a metal enclosure with plastic end-caps. Note the hole for delivering power with the two-way cable-mounting socket. Connecting the power the wrong way around will not damage the circuit, thanks to diode D1.
We measure gain versus frequency for 10 mVpp sinusoidal input for four A2088D-0 and compare to the ZHL-3A, which should provide flat gain up to 150 MHz. We are using a 300-MHz analog scope to measure output amplitude, and a 160-MHz function generator to provide the input.
We apply 12-ns, negative-going pulses to the input. We increase their height and record output pulse height.
[05-OCT-20] We define the following versions of the A2088D, each named after the length of the pulse it emits for an ideal input pulse of 1 ns. We define pulse width as the time between the pulse rising half-way to its peak and falling half-way from its peak, also known as the Full-Width Half-Height (FWHH).
|A2088D-0||No Shaper, L3 = 0 nH, C9 = 0 nF||≤10|
|A2088D-60||60-ns Shaper, L3 = 4.7 μH, C9 = 33 pF||63|
|A2088D-100||100-ns Shaper, L3 = 6.8 μH, C9 = 270 pF||100|
|A2088D-190||190-ns Shaper, L3 = 10 μH, C9 = 1.0 nF||190|
Our function generator produces pulses of no less than 10 ns. The A2088D-0 reproduces these 10-ns pulses faithfully, as shown below.
We measure gain versus frequency of the A2088D-0, using a 1-m RJ-58C/U cable from a synthesizer, and a spectrometer with 50-Ω input connected directly to the amplifier output. When we connect the synthesizer directly to the spectrometer we see −40±2 dBm. The amplifier output varies by far more.
[05-MAR-20] We damage three SiPMs by connecting power to them the wrong way around. There is an error in the power plug footprint of the A208801C printed ciruit board, and resistor R1 = 1 kΩ allows 30 mA to flow in the foreward direction through D1 when we connect 30 V to the anode. In the new circuit, we increase R1 to 10 kΩ, eliminate L1, and switch to board-edge right-angle connectors.
We lay out the A208801E. This board has space to put a 5-cm square scintillator over the SiPM, and holes for standoffs to mount the scintillator. Connectors are on the bottom side, right-angled near the board edge.
[26-AUG-20] As we report in Silicon Photomultipliers: Characterization and Cosmic Ray Detection, with two SiPM-scintillator combinations, we can detect coincident light pulses generated by cosmic muons. The screen shot below is one such pulse, fed directly into an oscilloscope.
The MICROFC data sheet gives 3.2 ns as the length of a single-photon pulse generated by the 6-mm square SiPM. Our pulse is 20 ns long. We do not know the relaxation time constant of our plastic scintillator, but we expect it to be no more than 4 ns. The pulse we observe here is 20 ns long.
[14-SEP-20] We assemble two SiPM A2088E boards together with their own scintillators.
The cable we use to connect the first SiPM to oscilloscope channel No1 is 1.5 m longer than the cable we use to connect the second to channel No2. We observe the following muon pulses in one event.
The No1 pulse is delayed by 8 ns with respect to the No2 pulse, which is consistent with the propagation delay of 1.5 m of coaxial cable.